Gain control of a power amplifier

ABSTRACT

The present invention presents an improved power control scheme for RF power amplifiers. The gain control signal used to control the power amplifier is subjected to pre-distortion (Hpre) before being supplied to the power amplifier, in order to reduce variations in control loop gain.

[0001] The present invention relates to telecommunications systems, and in particular to power control in mobile telephone systems.

BACKGROUND OF THE INVENTION

[0002] The requirements for output power control in mobile telephones can often be difficult to achieve. The requirements for GSM, for example, can be found in the ETSI specification “05.05 Digital cellular telecommunications system; Radio transmission and reception”. There are three critical parameters concerning the transmitter output power.

[0003] Output power level during a constant power part (“mid part”) of a transmitted burst.

[0004] Power vs. time, i.e. output power during up-ramping and down-ramping parts of a transmitted burst.

[0005] Spectrum due to switching (up- and down-ramping).

[0006] Several output power classes are specified in the 05.05 document. These power levels should be kept within well-defined tolerances.

[0007] The “power vs. time” requirements state that the transmitted power should fit within a specified template, of output power versus time. The template can be illustrated as a graph of power vs. time. Adjusting the telephone parameters so that they fit the power vs. time template can be a very time-consuming task during development and critical during manufacturing.

[0008] The spectrum due to switching requirement means that the spectrum caused by the ramping (switching) process should fit in a specified spectrum mask. It is therefore necessary to have a “good” (reliable) power vs. time behaviour, not only to fulfil the power vs. time template but also to avoid spectrum contamination.

[0009] It is to be noted that, although the GSM system is used as an example, the ideas presented in this specification could be used in any TDMA (Time Division Multiple Access) system, or any system that requires fast and/or accurate power control, such as CDMA.

[0010] Arranging the power control so that the telephone fits the power vs. time template and the spectrum due to switching mask, can be a very time-consuming task. In production, good yield is necessary.

[0011] In FIG. 1 of the accompanying drawings, the principle of today's power control solution is shown. A power amplifier 1 is connected to receive an RF input RF_(in). The power amplifier operates to output an amplified RF signal RF_(out) to an antenna 2, as is known and understood.

[0012] In order to control the power output of the power amplifier, the current, I_(c), used by the PA (Power Amplifier) 1, is measured (through a resistor R). This current value provides an indirect measurement of the PA output power. The measurement provided by voltage x₄=RI_(c), is fed back for comparison with an input control signal x₁. A difference (or error signal), x₂, is filtered by a loop filter, H_(LP), to produce a control signal x₃, which is used for controlling the PA RF output power. Signal x₃ is often called V_(apc) (apc=amplifier power control). Ideally, the measurement signal x₄ should track the input control signal x₁.

[0013] The total transfer function for the control system (H_(tot)=x₄/x₁) can be found from the following:

x ₄ =x ₃ H _(PA) =x ₂ H _(LP) H _(PA)=(x ₁ −x ₄)H _(LP) H _(PA)  (1)

x ₄(1+H _(LP) H _(PA))=x ₁ H _(LP) H _(PA)  (2) $\begin{matrix} {H_{tot} = {\frac{x_{4}}{x_{1}} = \frac{H_{LP}H_{PA}}{1 + {H_{LP}H_{PA}}}}} & (3) \end{matrix}$

[0014] Minimizing the difference between x₁ and x₄ would provide an ideal control loop. This means that x₄/x₁≈1, or H_(LP)H_(PA)>>1.

[0015] Ideally, the transfer function H_(PA)=x₄/x₃ should be constant(=I_(c)/V_(apc)). However, in practice, this is not generally the case. As illustrated in FIG. 2, the transfer function of the feedback loop typically varies, i.e. the feedback loop gain varies. This variation is due to the variation of the PA transfer function H_(PA) with the control voltage V_(apc). Thus, the maximum achievable error reduction of the control system will vary. In the FIG. 2 example, the loop is practically “open” for low V_(apc) and high V_(apc) values, causing poor tracking ability in the control system. For medium V_(apc) values however, the tracking ability is good, since the loop gain is high.

[0016] The non-constant behaviour of H_(PA) will also result in implementation difficulties for the loop filter since the risk of instability is high. The reason for this is that the loop filter must have sufficient gain to achieve good error reduction and fast control even at low or high V_(apc) values (where H_(PA) is small). On the other hand, this means increased risk for instability at medium V_(apc) values (where H_(PA) is large).

SUMMARY OF THE PRESENT INVENTION

[0017] The invention presented in this document adds a biasing pre-distortion block to the control loop shown in FIG. 1. By doing this, the behaviour of the PA control loop will have less loop gain variation, since the gain variations of H_(PA) is compensated for.

[0018] Distinguishing properties of the presented solutions are:

[0019] The power vs. time mask (in GSM specified in 05.05) should be more straightforward to fulfil, since variations in the loop gain due to variations in H_(PA) are reduced. This will make implementation of suitable loop filters easier.

[0020] Since power vs. time will be easier to control, this will also mean that it is easier to do the up-ramping and down-ramping in such a way that the spectral contamination is held low. Thus, the requirements on spectrum due to switching (in GSM specified in 05.05) will be easier to fulfil.

[0021] Although the GSM system is used as an example, the ideas presented in this report could be used in any TDMA (Time Division Multiple Access) system, or any systems that require fast and/or accurate power control.

[0022] It is emphasised that the term “comprises” or “comprising” is used in this specification to specify the presence of stated features, integers, steps or components, but does not preclude the addition of one or more further features, integers, steps or components, or groups thereof.

BRIEF DESCRIPTION OF THE DRAWINGS

[0023]FIG. 1 illustrates a prior art power amplifier and control circuit;

[0024]FIG. 2 illustrates a transfer function of the control circuit of FIG. 1;

[0025]FIG. 3 illustrates a power amplifier and control circuit embodying one aspect of the present invention;

[0026]FIG. 4 illustrates respective transfer functions of parts of the circuit in FIG. 3;

[0027]FIG. 5 illustrates a derivative of one of the transfer functions shown in FIG. 4;

[0028]FIG. 6 illustrates control loop gain in a practical example of the circuit of FIG. 3;

[0029]FIG. 7 illustrates a power amplifier and control circuit embodying another aspect of the present invention; and

[0030]FIG. 8 illustrates a power amplifier and control circuit embodying another aspect of the present invention.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT

[0031]FIG. 3 is a block diagram of a power amplifier and control circuit embodying one aspect of the invention. The FIG. 3 embodiment is similar to the circuit of FIG. 1. However, the FIG. 3 circuit includes an extra functional block, H_(pre), in the feedback control loop. The extra block H_(pre) introduces an additional term in the transfer function of the feedback control loop. The overall transfer function of the feedback control loop can be found from the following, with reference to FIG. 3: $\begin{matrix} \begin{matrix} {x_{5} = {x_{4}H_{PA}}} \\ {= {x_{3}H_{LP}H_{PA}}} \\ {= {x_{2}H_{pre}H_{LP}H_{PA}}} \\ {= {\left( {x_{1} - x_{5}} \right)H_{pre}H_{LP}H_{PA}}} \end{matrix} & (4) \end{matrix}$

 x ₅(1+H _(pre) H _(LP) H _(PA))=x ₁ H _(pre) H _(LP) H _(PA)  (5)

[0032] Which gives: $\begin{matrix} {H_{tot} = {\frac{x_{5}}{x_{1}} = \frac{H_{pre}H_{LP}H_{PA}}{1 + {H_{pre}H_{LP}H_{PA}}}}} & (6) \end{matrix}$

[0033] To produce an ideal feedback control loop, the difference between x₁ and x₅ should be minimized. This means that x₅/x₁≈1 or in other words H_(pre)H_(LP)H_(PA)>>1.

[0034] As discussed above, H_(PA) is not constant. However, it is desirable to make the transfer function H_(tot)=x₅/x₁ constant. If the loop filter (H_(LP)) is assumed to be linear (i.e. the gain is independent of input signal), H_(tot) can be made constant by choosing H_(pre)=kH_(PA) ⁻¹, where k is a constant. With H_(pre)=kH_(pa) ⁻¹ in equation (6), this gives: $\begin{matrix} {H_{tot} = \frac{{kH}_{LP}}{1 + {kH}_{LP}}} & (7) \end{matrix}$

[0035] In other words, by introducing a pre-distortion block, H_(pre)=kH_(PA) ⁻¹, in the feedback control loop, the overall loop gain can be made to be constant (i.e. independent of the power amplifier V_(apc)=x₄). FIG. 4 illustrates such ideal pre-distortion using H_(pre). In the ideal case, H_(pre)˜x₄/x₅. This can be seen to mean that H_(pre) is proportional to the inverse of the derivative of the function I_(c) vs. V_(apc). The function and its derivative are illustrated in FIG. 5.

[0036] However, it is not always necessary to eliminate completely variations in the loop gain by achieving perfect pre-distortion. In a solution for mobile telephones, for example, it could be acceptable to use an implementation that simply reduces the loop gain variations by a desired amount. FIG. 6 illustrates the PA transfer function (H_(PA)) and the resulting overall transfer function (H_(pre)H_(PA)) following use of the pre-distortion block in a practical embodiment.

[0037] The pre-distortion function H_(pre) can be implemented or calculated in several ways.

[0038] For example, by varying the gain H_(PA) of the PA 1 in real time, a circuit solution in the analogue domain can be used to determine H_(pre). An analogue circuit which has x₄ and x₅ as inputs can be used to determine H_(pre) such that variations in H_(TOT) are reduced. The signal “gain control” in FIG. 7 sets the gain of H_(pre).

[0039] Alternatively, H_(pre) can be calculated in the digital domain whilst varying the H_(PA) in real time. Again, both x₄ and x₅ are used as inputs for deciding proper gain control signal to supply to the pre-distortion block. The gain control signal is calculated to minimise variations in H_(TOT)

[0040] Alternatively, a burst-based learning solution can be used. In such a case, the gain of the predistortion block is first set constant (=1) during one burst. Values of x₄ and x₅ are sampled (collected) during this burst. The PA characteristic, H_(PA), is thereby obtained and a suitable H_(pre){x₅} (or H_(pre){x₄}) is then used during the call, for all bursts that have the same nominal (“mid-part”) power as the one that the H_(pre){x₅} (or H_(pre){x₄}) was meant for. When a “new” power level is requested for the first time during a call, the procedure is repeated, ie. x₄ and x₅ are collected and a H_(pre){x₅} (or H_(pre){x₄}) for this power level is calculated. H_(pre){x₅} (or H_(pre){x₄}) for different power levels are stored in a memory (table). When the H_(pre){x₅} (or H_(pre){x₄}) is to be used, first the memory address containing the table is addressed to find the data H_(pre){x₅} (or H_(pre){x₄}) associated with the power level that is to be sent. Then, during transmission of the burst, the elements in the table (on the memory address) are addressed with x₅ (or x₄).

[0041] As an alternative x₁ could be used to address the elements in a table containing H_(pre){x₁} The learning principle is the same as above, with the exception that not only values of x₄ and x₅ are sampled (collected) during the burst but also x₁.

[0042] As a further alternative, a learning procedure can be used during manufacture of the device concerned (telephone, for example). Tables, addressed with x₄ and/or x₅, are used for deciding proper gain in the pre-distortion block. For each power level (and with H_(pre)=constant=1), values of x₄ and x₅ are sampled (collected). Thus, the PA characteristic, H_(PA), is obtained and a suitable H_(pre){x₅} (or H_(pre){x₄}) for each power level can be computed. H_(pre){x₅} (or H_(pre){x₄}) for different power levels are stored in a memory (table). When the H_(pre){x₅} (or H_(pre){x₄}) is to be used, first the memory address containing the table is addressed to find the data H_(pre){x₅} (or H_(pre){x₄}) associated with the power level that is to be sent. Then, during transmission of the burst, the elements in the table (on this memory address) are address with x₅ (or x₄).

[0043] As an alternative, x₁ could be used to address the elements in a table containing H_(pre){x₁}. The “learn-up” principle is the same as described above, with the exception that not only values of x₅ and x₅ are sampled (collected) during the burst, but also x₁.

[0044] The learning procedure can also be used to produce tables for reference during use. The gain H_(pre) in the pre-distortion block then depends on what power level the telephone is requested to transmit on during the “mid part” of the burst.

[0045]FIG. 7 shows the principle of using the real time or burst variation of the H_(pre), to reduce loop gain variations due to gain variations in H_(PA).

[0046] In FIG. 8, the principles of using the tabular methods are illustrated. The gain of H_(pre) is varied in a manner that has been determined by the learning procedure described above.

[0047] Reducing variations in feedback loop gain means that the power vs. time mask in TDMA systems (in GSM this is specified in the 05.05 ETSI document) will probably be easier to fulfil. This will make implementation of suitable loop (filter) easier.

[0048] Since power vs. time will be easier to control, up-ramping and down-ramping will be possible in such a way that the spectral contamination remains low. Thus, the requirements on spectrum due to switching (in GSM this is specified in the 05.05 ETSI document) will probably be easier to fulfil. 

1. A power amplifier circuit comprising: a power amplifier having a control input, a signal input and a signal output, the amplifier having a gain value determined by a control signal applied to the control input of the amplifier; a measurement unit operable to produce a measurement signal indicative of an amount of electrical current drawn by the power amplifier; and a control unit comprising: an error detection unit operable to receive the measurement signal from the measurement unit, and operable to produce an error signal; and a signal processing unit operable to receive the error signal from the error detection unit, and to modify the error signal in a predetermined manner to produce a gain control signal for supply to the power amplifier as the said control signal.
 2. A circuit as claimed in claim 1, wherein the predetermined manner of modification of the error signal is determined as a function of the error signal and the measurement signal.
 3. A circuit as claimed in claim 1 or 2, wherein the error detection unit is operable to receive a reference signal and is operable to produce the error signal in dependence upon the reference signal and the measurement signal.
 4. A circuit as claimed in claim 3, wherein the reference signal is determined by stored reference values.
 5. A circuit as claimed in claim 3 or 4, wherein the predetermined manner of modification of the error signal is determined by a function of the error signal, the measurement signal and the reference signal.
 6. A circuit as claimed in any one of the preceding claims, wherein the signal processing unit is operable to distort the error signal so as to produce a gain control signal which substantially corrects for gain variations occurring in the power amplifier circuit.
 7. A circuit as claimed in any one of the preceding claims, wherein the predetermined manner of modification is selected by determining the error signal during a first burst of output power from the power amplifier.
 8. A circuit as claimed in any one of the preceding claims, wherein the predetermined manner of modification of the error signals is determined by reference to stored values.
 9. A circuit as claimed in claim 8, wherein the signal processing unit is operable to access stored values on the basis of a combination of the reference signal, the measurement signal and the error signal.
 10. An RF power amplifier circuit comprising: a power amplifier having RF signal input and output terminals and a gain control signal input, the amplifier having a RF gain value determined by a gain control signal received at the gain control signal input; and a control circuit for providing a gain control signal to the power amplifier, wherein the control circuit comprises: current measurement means operable to provide a measurement signal indicative of an amount of electrical current drawn by the power amplifier, error detection means operable to produce an error signal in dependence upon the measurement signal and a reference signal; and processing means operable to receive the error signal from error detection means and to apply a predetermined distortion to the gain control signal, the power amplifier, current measurement means, error detection means and processing means forming a feedback loop having a transfer function, the predetermined distortion applied by the processing means to the error signal serving to reduce variations in the transfer function of the feedback loop.
 11. A circuit as claimed in claim 10, wherein the predetermined distortion of the error signal is determined as a function of the error signal and the measurement signal.
 12. A circuit as claimed in claim 10 or 11, wherein the error detection means is operable to receive a reference signal and is operable to produce the error signal in dependence upon the reference signal and the measurement signal.
 13. A circuit as claimed in claim 12, wherein the reference signal is determined by stored reference values.
 14. A circuit as claimed in claim 12 or 13, wherein the predetermined distortion of the error signal is determined by a function of the error signal, the measurement signal and the reference signal.
 15. A circuit as claimed in any one of claims 10 to 14, wherein the processing means is operable to distort the error signal so as to produce a gain control signal which substantially corrects for gain variations occurring in the power amplifier circuit.
 16. A circuit as claimed in any one of claims 10 to 15, wherein the predetermined distortion is selected by determining the error signal during a first burst of output power from the power amplifier.
 17. A circuit as claimed in any one of claims 10 to 16, wherein the predetermined distortion of the error signal is determined by reference to stored values.
 18. A circuit as claimed in claim 17, wherein the processing means is operable to access stored values on the basis of a combination of the reference signal, the measurement signal and the error signal.
 19. A method of controlling the output power of a power amplifier circuit, the method comprising: measuring an electrical current drawn by a power amplifier; producing an error signal in dependence upon the measured current and a reference signal; applying a predetermined modification to the error signal to produce a gain control signal which reduces variations in the transfer function of the feedback loop.
 20. A method as claimed in claim 19, wherein the predetermined modification is determined as a function of the measured current and the gain control signal.
 21. A method as claimed in claim 19 or 20, wherein the predetermined modification is determined from a look up table containing known modification factors.
 22. A method as claimed in claim 19, 20 or 21, wherein the reference signal is determined by stored reference values.
 23. A method as claimed in claim 19, 20, 21, or 22, wherein the predetermined modification of the error signal is determined by a function of the error signal, the measurement signal and the reference signal.
 24. A method as claimed in any one of claims 19 to 23, wherein the predetermined modification is selected by determining the error signal during a first burst of output power from the power amplifier.
 25. A method as claimed in any one of claims 19 to 24, wherein the predetermined modification of the error signal is determined by reference to stored values.
 26. A method as claimed in claim 25, conmprising accessing stored values on the basis of a combination of the reference signal, the measurement signal and the error signal. 